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Class AB amp using TIP102. Seeking Critique
Class AB amp using TIP102. Seeking Critique
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Old 29th March 2017, 08:26 PM   #1
jlny is offline jlny  United States
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Default Class AB amp using TIP102. Seeking Critique

Hello All,
I have recently been working on making some improvements to a small power amplifier I made back about a year ago (see result of that thread here). Since then, I have done a few iterations on the design, both to increase the output power and to add current regulation to the biasing to reduce any mains hum.

My question is, how can I improve this design? I am still fairly new to all this, so I'm always looking for ways to improve my designs or catch mistakes. I have not done any physical testing of this circuit, so I do not yet know if it will actually work.

A few notes on this design:

1. The design is meant to be powered nominally from a single-ended 48V supply, but the bias current adjustment at R5 should allow for a power supply range of about 36-65V. The speaker impedance is 8 Ohms nominal, but is designed to also work down to a 4 Ohm speaker impedance.

2. In an effort to increase the efficiency, I have opted to use TIP102/107 Darlington pair transistors instead of the IRF540N/9540N MOSFETs as with my previous design, and I made some changes to the output stage. (Please note that the Eagle Schematic does not show the transistors as being Darlington pairs, but that is mainly because I am just using a generic TO-220 transistor package for when I do the PCB layout.)

3. The three pairs of TIP102/107s may not all be populated on the final board depending on the supply voltage, speaker impedance, and heatsinking configuration. I could probably get by with one or two pairs, but I also plan to experiment with rearranging the feedback to try ganging two together in a differential configuration, so I'm planning to play it safe on the thermal side.

4. The adjustment trimmer on Q11 should allow for use with either darlington BJTs or MOSFETs interchangeably, in which case I would populate R21 and R22 with 220 Ohm resistors or similar (I'm open to suggestions for the exact value on that ). Q11 will also be mounted on the heatsink with the power stage.

5. THD at 1kHz and 1Vrms output was calculated at approx. 0.01% for the 1st 5 harmonics. THD at 10Vrms was calculated at closer to 0.006%. What is a good frequency and or output level for calculating THD? I couldn't seem to find much info on any kind of standard values for testing THD.

6. Phase margin is approximately 56.5 degrees. Gain margin is 19.75 dB. I have included two bode plots, one including the input filter and one that bypasses it for when I calculated the phase/gain margins.

7. I originally was going to simulate for the current regulating transistors in the PSpice model, but I was exceeding the allowed limit for transistors in Orcad, so unfortunately I had to simplify the schematic with ideal current sources instead. All component designations (e.g. R10, Q3, etc.) should be based on the Eagle Schematic.

My plan is to try this circuit out on a breadboard, then eventually draft up a PCB layout of the final design. I have made a lot of changes back and forth between the simulation and schematic, but they should hopefully match up for all of the values shown.

Please let me know your thoughts and any corrections and/or improvements.
Attached Images
File Type: png Eagle Schematic r0.png (61.4 KB, 434 views)
File Type: png pspice schematic r0.png (22.0 KB, 421 views)
File Type: png bode plot r0 amp only.png (17.9 KB, 403 views)
File Type: png bode plot r0 with input filter.png (19.8 KB, 387 views)
File Type: png THD results r0.png (12.8 KB, 381 views)
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Old 29th March 2017, 08:40 PM   #2
rayma is offline rayma  United States
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Quote:
Originally Posted by jlny View Post
How can I improve this design?
The negative feedback loop capacitor should be much larger, at least 100uF or more, instead of 10uF.

Last edited by rayma; 29th March 2017 at 08:44 PM.
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Old 29th March 2017, 09:58 PM   #3
Mark Johnson is online now Mark Johnson  United States
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Class AB amp using TIP102. Seeking Critique
  • Many people, including the designer of the Threshold S300 (Nelson Pass), like to short together the collectors when using several Sziklai pairs in parallel. See attached schematic. In post #1 figure 2, that would be the collectors of Q15-Q16-Q17 and also the collectors of Q18-Q19-Q20.
  • The AC gain is awfully high: (R25+R26)/R26 = 34X. Power amps usually have an AC gain more like 20X.
  • I'd be more comfortable if R24 was an adjustable trimmer pot instead of a fixed resistor, so I could dial in the desired bias current within half a milliamp.
  • I'd be tempted to try out the advice Douglas Self hammers again and again in his power amp book: be sure to insert an emitter follower between the input stage (collector of Q2) and the voltage amplification stage (base of Q3). This lightens the load driven by the input stage, and helps the compensation capacitor (C5) work its pole-splitting magic.
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File Type: jpeg s150-300-500.jpeg (137.3 KB, 206 views)
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Old 29th March 2017, 10:03 PM   #4
sgrossklass is offline sgrossklass  Germany
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I'd have my doubts about the output stage design. Move the 0.22s to the Darlingtons' emitters instead, give Q12/13 some dedicated emitter resistors (EDIT: like what Mark Johnson shows above), and play with R23/R24 to obtain a decent bias point (the high and dominant 3rd distortion indicates things are almost certainly underbiased).
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Old 29th March 2017, 10:29 PM   #5
jlny is offline jlny  United States
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Rayma, Thanks for the suggestion. I calculated 10uF to come out to a low-frequency cutoff of around 16Hz (1/(2*PI*1000*1E-5)=15.92). What is the benefit of making it higher?

Mark,
Hmm, that seems like a good idea. Looking at my circuit again, it probably makes sense to put the 0.22 Ohm resistors on the emitters of the output transistors instead of the collectors.

Really? I recall being told last time around that the "de facto" standard was around 29dB? See here.

R23/R24 on the Pspice schematic is meant as a 10k, 10-turn trimmer and a 1k resistor in series, as shown on the Eagle schematic I recommend going by the numbering on the Eagle Schematic, since it actually has all of the components shown. (I was too lazy to make the designations match lol).

Definitely doable. I'll mess around with it.

Thanks for the advice!
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Old 29th March 2017, 10:36 PM   #6
rayma is offline rayma  United States
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Quote:
Originally Posted by jlny View Post
I calculated 10uF to come out to a low-frequency cutoff of around 16Hz
(1/(2*PI*1000*1E-5)=15.92). What is the benefit of making it higher?
This capacitor is part of the negative feedback loop, and is critical. To minimize distortion,
it should have low enough impedance that there is virtually no signal voltage across it.

Also, the input HP filter has the same time constant, and these poles should be staggered.
Since the input filter is set at 16Hz, all other circuit poles should be lower in frequency by several octaves.
This goes for the emitter bypass capacitor on the VA as well, it should be around 1000uF, rather than 100uF.

Last edited by rayma; 29th March 2017 at 11:00 PM.
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Old 30th March 2017, 01:48 AM   #7
DUG is offline DUG  Canada
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16Hz 3dB

Single roll-off.

The effect of double roll-off:

Hz single double
2.0 -16.5 -32.9
2.3 -15.5 -31.0
2.6 -14.5 -29.0
3.0 -13.5 -27.0
3.5 -12.5 -25.0
4.0 -11.5 -23.0
4.6 -10.5 -21.0
5.3 -9.5 -19.0
6.1 -8.5 -17.0
7.0 -7.6 -15.1
8.0 -6.6 -13.3
9.2 -5.8 -11.5
10.6 -4.9 -9.9
12.1 -4.2 -8.4
13.9 -3.5 -7.0
16.0 -2.9 -5.8
18.4 -2.3 -4.7
21.1 -1.9 -3.8
24.3 -1.5 -3.0
27.9 -1.2 -2.4
32.0 -0.9 -1.9
36.8 -0.7 -1.4
42.2 -0.6 -1.1
48.5 -0.4 -0.9
55.7 -0.3 -0.7
64.0 -0.3 -0.5
73.5 -0.2 -0.4
84.4 -0.1 -0.3
97.0 -0.1 -0.2

3dB is actually closer to 24Hz and 1dB about 45Hz

I go with rayma at 10 X lower.

Last edited by DUG; 30th March 2017 at 02:12 AM.
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Old 30th March 2017, 02:52 PM   #8
jlny is offline jlny  United States
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All,
I have made some of the recommended changes to the design. Please see the updated schematic.

changes are:
-changed 0.22 Ohm resistors to be at the emitters instead of the collectors, added additional 0.22 Ohm resistors to the emitters of Q13 and Q14.
-changed C3 to 100uF, C4 to 47uF, and C6 to 1000uF.
-changed R25 to 27k instead of 33k, for a gain of 27.

simulations show 3dB cutoffs at 16.5Hz and 76kHz with the input filter included. THD is still around 0.01% at 1VRMs out for about 100mA bias current per pair. phase/gain margins are 56.3 degrees and 19.4dB, respectively.

I tried adding an emitter follower between Q7 and Q12, but it actually made the circuit unstable in simulation. The worst-case current gain of the power stage should be around 6000 for 1 pair of TIP10Xs, and around 30000 for 3 pairs, so the amplification stage only runs at a bias current of 7mA, and even that is probably more than I need. Q12 should be pretty sensitive, so is the emitter follower necessary?

I also tried changing R25 to 22k for a gain closer to what Mark recommended, but the simulation didn't really show any difference in stability or distortion, so I would prefer to keep the slightly higher gain.

If I were to use a capacitor with a lower voltage rating than the supply voltage for C6, would it make sense to add a zener across it? on paper, the voltage across C6 will never be that high.
Attached Images
File Type: png Eagle Schematic r1.png (61.5 KB, 166 views)
File Type: png THD results r1.png (9.5 KB, 88 views)
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Old 30th March 2017, 04:54 PM   #9
jlny is offline jlny  United States
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All,
In light of my own comment above about the bias current on Q12, I have changed the circuit to use a 2.6mA bias current instead of a 7mA bias current.

This allows me to increase R3, R6, and R14 to 10k (the original 4.7k resistors would have been probably 1W resistors for safety, so hopefully now I can dial that back to 1/2W 10k resistors). R7, R15, and R18 have been changed to 270 Ohms, C4 has been changed back to 22uF, and C6 has been changed to 330uF (all of these values should have a low-frequency cutoff below 2 Hz).

I have also changed R23/R24 and R26-R31 to 0.47 Ohms, if only for the reason that the current biasing trimmer will be really sensitive even if I use a 10-turn trimmer. I may add another resistor to Q11 just to narrow the range a bit. C2 and C5 have been increased to 2.2nF to improve phase margins.

THD=0.005% for 100mA/pair, PM/GM = 66degrees/14.5dB. 3dB cutoffs with the input filter are around 16.5Hz and 32.5kHz.

Let me know if you have any additional corrections or thoughts.
Attached Images
File Type: png Eagle Schematic r2.png (61.5 KB, 69 views)
File Type: png THD results r2.png (10.0 KB, 67 views)

Last edited by jlny; 30th March 2017 at 05:22 PM.
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Old 30th March 2017, 07:18 PM   #10
sgrossklass is offline sgrossklass  Germany
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It's kinda getting there.

A 2n2 compensation cap (C5) is extremely high, normal values tend to be around 47-100 pF, maybe 150 pF on a seriously old/slow design. You're not even in the ballpark. With some bad luck your output stage is a hopeless mess of poles. Slew rate can't be too high in any case, what's it like? A 2n2 C2 also is quite heavy.

R23/24 strike me as way low and could let driver currents become dangerously high, try something more like 10-47 ohms.
CFP output stages often benefit from some Miller capacitance on the pnp driver, so try something 100pF-ish on Q14.
I'm not sure whether you really need R13, but a few hundred ohms (or even R || RC) in the bases of Q13 and Q14 seem worth a shot.

Not sure how fast Q11 would still be at only 2.6 mA, but you've got a bypass cap at least. The bias circuit does not strike me as failsafe should the pot wiper ever go open. Try 1k || 10k pot in the lower leg and a resistor in the upper leg that gives your a decent bias adjustment range (start with 820-910R or so).

Speaking of bias, what sort of current does each pair of Darlingtons get? I would hope for 30-50 mA, and try up to 100 with emitter resistors down to 0.22.

You're also missing an output series LR network (~1.5 H || 10R).

Using a current source for input bias seems overly fancy, anything wrong with a 10k / 10k||22 divider followed by a 22-100k? Once you've got compensation sorted, I'd also consider running the inputs a bit less hot, 500 nA at 100-220 ohms of degeneration should also do just fine while giving less potential for input impedance distortion.

Wait, does distortion really say 4.8e-3 %, i.e. 0.00048%? That's unloaded though, isn't it? And at little over 1 Vrms output, too, apparently.

Last edited by sgrossklass; 30th March 2017 at 07:28 PM.
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